High Sensitive Position Sensor based on PDH technique

Team members

Angela Anna Baiju and Chenyue Gu

Idea

This project is aiming of using Pound–Drever–Hall (PDH) technique to sense the vibration and the movement of the mirror driven by the noise from the environment (acoustic, thermal, etc.).

Pound–Drever–Hall laser frequency stabilisation is a powerful technique providing a means to stabilise the frequency of a laser to a specific reference frequency. It is commonly employed in precision measurements and experimental setups where precise control over the laser frequency is required, such as interferometric gravitational-wave detector. Alternatively, if a stable laser is available, the PDH technique can be used to stabilise and/or measure the instabilities in an optical cavity length via the error signal readout from the cavity.

In this project, we will lock the cavity by reading the error signal of reflection/transmission of the cavity and then feed it back to the input mirror, moving the mirror with a PZT. And then we can read out the cavity length change from the error signal. This sensing technique is commonly using in LIGO-Virgo-KAGRA (LVK) interferometric gravitational wave detection community, as well as quantum optomechnics.

Pound-Drever-Hall Method

The idea behind the PDH method is simple: A laser’s frequency is measured with a Fabry–Perot cavity, either transmission or reflection, and then is fed back to the input laser to suppress frequency fluctuations. The process begins with modulating the laser light. This is typically achieved by imposing a high-frequency (radio frequency or microwave) signal onto the laser beam (Local Oscillator). This modulation creates sidebands around the carrier frequency of the laser light. These sidebands are symmetrically spaced around the carrier frequency. The modulated laser light then passes through an electro-optic modulator (EOM). The EOM applies phase modulation to the light, causing the sidebands to shift in frequency relative to the carrier frequency. The amount of phase modulation applied determines the frequency separation between the carrier and the sidebands. The phase-modulated laser light is directed onto a frequency reference, which can be a stable Fabry–Perot cavity. The reflected beam is then picked off and compared with the local oscillator's signal via a mixer whose output is the product of its inputs. From the output of the mixer, by using a low-pass filter, the dc (or very low frequency) part which is of interest remains and the ac (or high frequency) part that is usually the twice the modulation frequency is filtered out. The remaining dc signal, so called error signal, then goes through the feedback loop. The feedback loop typically involves a control mechanism, such as adjusting the current supplied to the laser diode or controlling the frequency of the modulation signal. The feedback loop aims to minimise the error signal by stabilising the laser frequency to match the reference frequency. A basic setup of PDH method is shown in Fig. 1 .

Fig. 1 A basic diagram of the setup implementing Pound-Drever-Hall method. In this digram, the laser frequency is modulated with a Pockels cell, driven by some local oscillator. The reflected beam is picked off with an optical isolator (a polarising beamsplitter and a quarter-wave plate makes a good isolator) and sent into a photodetector, whose output is compared with the local oscillator’s signal via a mixer. A low-pass filter on the output of the mixer isolates this low frequency signal, which then goes through a servo am- plifier and into the tuning port on the laser, locking the laser to the cavity. The Faraday isolator keeps the reflected beam from getting back into the laser and destabilizing it.

To implement the method, we need to know well about how to process the error signal, which is the heart of the technique. We follow the derive from Eric D. Black's paper , and run simulation by Python.

Reflection of a monochromatic beam from a Fabry-Perot cavity

To start the math behind it, we pick a point outside the cavity and measure the electric field over time. Then the magnitude of the electric field of the incident and the reflected beams can be written as

$E_{in}=E_{0}e^{i\omega t}$,

$E_{re}=E_{1}e^{i\omega t}$,

where $\omega$ is the incident laser frequency, $E_{0}$ and $E_{1}$ are complex, and in this way, we account for the relative phase between the two waves in. The reflection coefficient $F(\omega )$ is thus given by

$F(\omega )=E_{re}/E_{in}={\frac {r\left(e^{i{\frac {\omega }{\Delta \nu _{FSR}}}}-1\right)}{1-r^{2}e^{i{\frac {\omega }{\Delta \nu _{FSR}}}}}}$.

Here we consider a lossless and symmetric Fabry-Perot cavity formed with two mirrors whose amplitude reflection coefficient are both $r$. The free spectral range of the cavity is denoted as $\Delta \nu _{FSR}=c/2L$.

Fig. 2 Magnitude and phase of the reflection coefficient for a Fabry-Perot cavity. The finesse is different for the figure of different rows. According to different $r=0.99,0.90,0.75$, from the top row the the bottom row, the figures show the reflection coefficient for cavities of fitness equals to $312.58$, $29.80$, and $10.88$ respectively. Note the discontinuity in phase (the straight line around $\omega /\Delta \nu _{FSR}=2\pi$), caused by the reflected power vanishing at resonance.

Noted that $F(\omega +2\pi n\Delta \nu _{FSR})=F(\omega )$, so the cavity has infinite resonant frequencies at $\omega _{c}=2\pi n\Delta \nu _{FSR}$ (where $n$ is an integer), and here we just plot the reflection coefficient around one cavity resonance as an example.

Modulating the beam: sidebands and the error signal

As shown in figure 2, when the frequency of the incident beam is detuned away from the resonance ($\omega /\Delta \nu _{FSR}>2n\pi$ or $\omega /\Delta \nu _{FSR}<2n\pi$), one can not tell the difference between blue- (higher frequency) and red-(lower frequency) detuning by looking at the magnitude (intensity) of the reflection coefficient. This is because the magnitude of the reflection coefficient is symmetric about the cavity resonant frequency. However, the phase profile near the resonance does not have this feature. Instead, it has a huge change and is discontinuous. Thus, to tell whether the laser's frequency is above or below the cavity resonance, we need to measure the phase of the reflected beam. In order to do so, we need to modulate the beam and generate sidebands with a definite phase relationship to the incident and reflected beams. After interfering these sidebands with the reflected beam, we will get a beat pattern at the modulation frequency, which gives the information of the phase of the reflected beam.

Creating the sidebands

Now, we apply a phase modulation on the input field, and we can write its electric field as

$E_{in}=E_{0}e^{i(\omega t+\beta sin\Omega t)}$,

where $\Omega$ is the modulation frequency, and $\beta$ is the modulation depth. Thus, we can write the expansion of this expression with Bessel function as

$E_{in}\approx \left[J_{0}(\beta )+2iJ_{1}(\beta )sin\Omega t\right]e^{i\omega t}=E_{0}\left[J_{0}(\beta )e^{i\omega t}+J_{1}(\beta )e^{i(\omega +\Omega )t}-J_{1}(\beta )e^{i(\omega -\Omega )t}\right]$.

It shows that after the modulation, there are actually three different beams incident on the cavity: a carrier with angular frequency of $\omega$ and two sidebands with frequencies of $\omega \pm \Omega$. And if we denote the total power of the incident beam as $P_{0}\equiv |E_{0}|^{2}$, the power of the carrier and the first-order sidebands can be written as

$P_{c}=J_{0}^{2}(\beta )P_{0}$,

$P_{s}=J_{1}^{2}(\beta )P_{0}$.

With a small modulation depth ($\beta <1$), we can assume all the power is in the carrier and the first-order sidebands ($P_{c}+2P_{s}\approx P_{0}$).

Measuring the error signal

After modulation, the total reflection is written as the sum of the reflection of the carrier and two sidebands

$E_{re}=E_{0}\left[F(\omega )J_{0}(\beta )e^{i\omega t}+F(\omega +\Omega )J_{1}(\beta )e^{i(\omega +\Omega )t}-F(\omega -\Omega )J_{1}(\beta )e^{i(\omega -\Omega )t}\right]$

And the power of the reflected beam can then be obtained as

$P_{re}=|E_{re}|^{2}=P_{c}|F(\omega )|^{2}+P_{s}\left[|F(\omega +\Omega )|^{2}+|F(\omega -\Omega )|^{2}\right]$

$~~+2{\sqrt {P_{c}P_{s}}}\left[{\mathcal {Re}}\left(F(\omega )F^{*}(\omega +\Omega )-F^{*}(\omega )F(\omega -\Omega )\right)cos\Omega t+{\mathcal {Im}}\left(F(\omega )F^{*}(\omega +\Omega )-F^{*}(\omega )F(\omega -\Omega )\right)sin\Omega t\right]$

$~~~+(2\Omega ~term)$,

where we show the production of the three different frequencies, the carrier at $\omega$ and the upper and the lower sidebands at $\omega \pm \Omega$. We ignored the $2\Omega$ term which comes from the sidebands interfering with each other.

As shown in the equation, we get dc components related to the carrier and the two sidebands frequencies, and a sine term and a cosine term oscillating at the modulation frequency. We are interested in the oscillating terms because they carry the information of the phase of the reflected carrier. And we will see in the following, usually, at low modulation frequencies only the cosine term survives, and at high modulation frequencies, only the sine term is important.

Now we multiply the reflection signal with the modulation frequency ($sin\Omega t$) with a mixer, we get

$P_{mix}=P_{re}sin\Omega t=P_{I}+P_{dc}sin\Omega t-{\frac {1}{2}}P_{I}cos2\Omega t$,

where

$P_{dc}=P_{c}|F(\omega )|^{2}+P_{s}\left[|F(\omega +\Omega )|^{2}+|F(\omega -\Omega )|^{2}\right]$,

$P_{I}=2{\sqrt {P_{c}P_{s}}}{\mathcal {Im}}\left(F(\omega )F^{*}(\omega +\Omega )-F^{*}(\omega )F(\omega -\Omega )\right)$,

and we see in the mixed signal, the cosine term in the reflection is totally vanished. So in order to gain the information from the cosine term, we need to turn the sine signal into a cosine signal, so we can simply adding $\pi /2$ a phase shift, which can we achieved by a phase shifter or a delay line.

Then we will get

$P_{mix}=P_{re}cos\Omega t=P_{R}+P_{dc}cos\Omega t+{\frac {1}{2}}P_{R}cos2\Omega t$,

where

$P_{R}=2{\sqrt {P_{c}P_{s}}}{\mathcal {Re}}\left(F(\omega )F^{*}(\omega +\Omega )-F^{*}(\omega )F(\omega -\Omega )\right)$.

After the mixer, the information in the cosine and sine terms in the reflection signal are now become the only dc signal in the mixed signal. Then we can isolate them with a low-pass filter.

Fast modulation near resonance

In the regime when the carrier is near resonance and the modulation frequency is high enough ($\Omega \gg \Delta \nu _{FSR}/{\mathcal {F}}$) that the sidebands are not, we can assume that the sidebands are totally reflected that $F(\omega \pm \Omega )\approx -1$. Thus

$F(\omega )F^{*}(\omega +\Omega )-F^{*}(\omega )F(\omega -\Omega )\approx -i2{\mathcal {Im}}[F(\omega )]$,

is purely imaginary. In this regime, we mixed the reflection signal with the in-phase modulation signal and get the error signal as

$\epsilon =P_{I}=2{\sqrt {P_{c}P_{s}}}{\mathcal {Im}}\left(F(\omega )F^{*}(\omega +\Omega )-F^{*}(\omega )F(\omega -\Omega )\right)$.

Figure 3 shows a plot of this error signal.

Figure 3. Error signal with high frequency modulation. From left to right, the figures show the error signal for cavities of fitness equals to $312.58$, $29.80$, and $10.88$ respectively.

Slow modulation

When the modulation signal is very slow ($\Omega \ll \Delta \nu _{FSR}/{\mathcal {F}}$), we get the instantaneous frequency of the modulated beam as

$\omega (t)={\frac {d}{dt}}(\omega t+\beta sin\Omega t)=\omega +\Omega \beta cos\Omega t$

Then the reflected power can be written as

$P_{ref}(\omega +\Omega \beta cos\Omega t)\approx P_{ref}(\omega )+{\frac {dP_{ref}}{d\omega }}\Omega \beta cos\Omega t\approx P_{ref}(\omega )+P_{0}{\frac {d|F(\omega )|^{2}}{d\omega }}\Omega \beta cos\Omega t$,

and in this regime, the expression of $F(\omega )F^{*}(\omega +\Omega )-F^{*}(\omega )F(\omega -\Omega )$ is purely real as shown in the following:

$F(\omega )F^{*}(\omega +\Omega )-F^{*}(\omega )F(\omega -\Omega )\approx 2{\mathcal {Re}}[F(\omega ){\frac {d}{d\omega }}F^{*}(\omega )]\Omega \approx {\frac {d|F|^{2}}{d\omega }}\Omega$.

So in the reflection signal, only cosine term survives for the ac signal part. So, we should mix it with a shifted modulation signal, and we will get the error signal as (after the low pass filter)

$\epsilon =P_{0}{\frac {d|F|^{2}}{d\omega }}\Omega \approx 2{\sqrt {P_{c}P_{s}}}{\frac {d|F|^{2}}{d\omega }}\Omega$.

Figure 4 shows the signal with a low frequency modulation.

Experiment Diagram

We plan for a setup.... (the whole setup and explain how we applied the PDH locking)

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Reference

• Black, E. D. (2001). An introduction to Pound–Drever–Hall laser frequency stabilization. American journal of physics, 69(1), 79-87.